3W高精度恒流led照明驱动芯片SM7513
T1
R1
4 VCC
SM7513
GND 5
C1
U1
BOM 表： 位号 DB1 D1 R1 R2 E1 变压器参数： 参数 MB6S US1D 2.7R/1206 11K/0805 4.7uF/400V 位号 E2 C1 F1 U1 T1 参数 10uF/25V 1uF/16V 10R 1/4W 绕线电阻 SM7513 EE10(4+4)卧式
SM7513 恒流原边控制功率开关 v1.6
SM7513
特点
拓扑结构支持：反激及低成本 BUCK-BOOST 采用 730V 单芯片集成工艺 宽电压 90Vac~264Vac 输入电压范 围内恒流精度小于±5% 全电压范围内兼容 1-3W 明微专利的无需辅助绕组的原边 反馈控制技术可使系统节省光 耦、431 等元件 无需环路补偿 内置前沿消隐电路(LEB) 逐周期峰值电流比较 输出开/短路保护 内置开机软启动 无需 FB 反馈引脚 封装形式：SOP8 SOP8
TLEB
TDEM_MIN DMAX RDSON BVD_SS Vcc_uvlo TDEM_max
%
Ohm V V uS
注：如需最新资料或技术支持，请与我们联系
-2-
SM7513 恒流原边控制功率开关 v1.6
功能表述
SM7513 芯片是应用于离线式小功率 AC/DC 开关电源的高性能原边反馈控制功率开关芯片，全电压输入范 围内，恒流输出精度小于±5%。SM7513 芯片通过原边采样的方式来控制系统的输出，内部集成高压功率 MOS 管，节省光耦和 TL431 等元件。芯片内部集成了逐周期峰值电流限制，输出开/短路保护和开机软启动等保护功 能，以提高系统的可靠性。 启动和控制 SM7513 芯片内部集成高压功率开关，通过高压启动，省掉传统电路的外部启动电阻，以及辅助绕组的供 电电路，极大的降低了系统成本。 工作原理 SM7513 芯片要实现原边高精度的恒流控制，反激电源应用系统必须工作在不连续模式(DCM)下。芯片通过 检测原边绕组的反激电压，来控制输出电流电压。输出电流仅由变压器的匝比及峰值电流控制：
其中 LP 为原边绕组电感量，IP 为原边绕组峰值电流。由公式 3 可知，原边绕组电感量的改变会导致最大输 出功率和恒流模式下输出的恒流电流的变化。为了补偿原边电感量变化，芯片内部环路将开关频率锁定，锁定 的开关频率可表示为：
FSW
4 7 TDEMAG
(4)
因为消磁时间 TDEMAG 和电感量成反比， 通过频率锁定，LP 和 FSW 的乘积保持不变。所以最大输出功率和恒 流模式下的恒流电流不会随电感量变化。SM7513 芯片能最大补偿电感量±10%的变化。 电流检测和 LEB SM7513 芯片通过 CS 端检测外置检测电阻上的电压控制功率开关管的动作， 从而实现对变压器原边电流控 制，提供逐周期峰值电流限制。 为了消除高压功率管在开启瞬间产生的尖峰造成的干扰，内置前沿消隐电路，避免芯片在功率管开启瞬间 产生误动作，这样就可以省去外围 RC 滤波电路，节约系统成本。 保护控制 SM7513 芯片完善的各种保护功能提高了电源系统的可靠性，包括：逐周期峰值电流限制，输出短路保护， 软启动控制等。
注：控制变压器漏感可省去吸收电路
注：如需最新资料或技术支持，请与我们联系
-5-
SM7513 恒流原边控制功率开关 v1.6
SM7513 60V/60mA BUCK-BOOST 电源方案 原理图：
F1 DB1
8 7 6
DRAIN DRAIN GND GND
D1
5
Vout-
U1
AC C1
L1
4 VCC
概述
SM7513 是应用于离线式小功率 AC/DC 开关电源的高性能的原边反 馈控制功率开关芯片，在全电压输入范围内实现高精度恒流输出，精 度小于±5%，无需环路补偿，并可使系统节省光耦，TL431 以及变压器 辅助绕组等元件，降低成本。 芯片内部集成了逐周期峰值电流限制，输出开/短路保护和开机软 启动等保护功能，以提高系统的可靠性。
SM7513
3 EM 2 NC 1 CS
C3
R2
R1
C2
Vout+
BOM 表： 位号 DB1 D1 R1 R2 C1 参数 MB6S ES1J 2.4R /1206 100K /0805 4.7uF/400V 位号 C2 C3 F1 L1 U1 参数 1uF/16V 0805 10uF/100V 1206 10R 1/4W 线绕电阻 3mH/饱和电流>400mA SM7513
极限参数
极限参数(TA= 25℃) 符号 VCC VEM VCS TA Tstg VESD Rθja VDS 说明 芯片工作电压 EM 输入电压 CS 输入电压 工作温度 存储温度 人体放电模式 热阻 VDS 耐压 范围 -0.3~6 -0.3~6 -0.3~7.0 -20~125 -40~150 4 65 -0.3~730 单位 V V V ℃ ℃ KV ℃/W V
4 VCC
SM7513
3 EM 2 NC 1 CS
GND
GND
8
1 NP 2 NS 5 8
1 4 底视图
进线 制作说明：
5
1 . 骨 架 E E 1 0 (4 + 4 ) 卧 式 P C 4 0 磁 芯 2 . 电 感 量 L p (2 → 1 )= 2 .4 m H ， 漏 感 为 L p 的 5 % 以 下 3 . 初 级 对 次 级 打 1 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s 4 . 初 级 对 磁 芯 打 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s N S (8 → 5 ) Φ 0 .2 5 * 1 * 3 0 T N P (2 → 1 ) Φ 0 .1 5 * 1 * 1 4 6 T 5 . 次 级 对 磁 性 打 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s 6 . D C 5 0 0 V 绕 组 与 磁 芯 之 间 1 m in 大 于 1 0 0 M Ω 7 . D C 5 0 0 V 绕 组 与 绕 组 之 间 1 m in 大 于 1 0 0 M Ω
注：如需最新资料或技术支持，请与我们联系
-3-
SM7513 恒流原边控制功率开关 v1.6
典型应用方案
SM7513 10V/300mA LED 高端照明应用方案 原理图：
F1 DB1
8 7 6 5
T1
D1 Vout+ E2 R2 Vout-
DRAIN
DRAIN
AC U1 E1
R1
C1
BOM 表： 位号 DB1 D1 R1 R2 E1 变压器参数： 参数 MB6S US1D 2.7R/1206 11K/0805 4.7uF/400V 位号 E2 C1 F1 U1 T1 参数 10uF/25V 1uF/16V 10R 1/4W 绕线电阻 SM7513 EE10(4+4)卧式
注：如需最新资料或技术支持，请与我们联系
-6-
SM7513 恒流原边控制功率开关 v1.6
封装形式
SOP8
注：如需最新资料或技术支持，请与我们联系
-7-
8
1 NP 2 NS 5 8
1 4 底视图
进线 制作说明：
5
1 . 骨 架 E E 1 0 (4 + 4 ) 卧 式 P C 4 0 磁 芯 2 . 电 感 量 L p (2 → 1 )= 2 .4 m H ， 漏 感 为 L p 的 5 % 以 下 3 . 初 级 对 次 级 打 1 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s 4 . 初 级 对 磁 芯 打 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s N S (8 → 5 ) Φ 0 .2 5 * 1 * 3 0 T N P (2 → 1 ) Φ 0 .1 5 * 1 * 1 4 6 T 5 . 次 级 对 磁 性 打 5 0 0 V A C 漏 电 流 < 2 m A /6 0 s 6 . D C 5 0 0 V 绕 组 与 磁 芯 之 间 1 m in 大 于 1 0 0 M Ω 7 . D C 5 0 0 V 绕 组 与 绕 组 之 间 1 m in 大 于 1 0 0 M Ω
Io 2 / 7 N I P
注：Io 为输出电流；N 为变压器匝比； 工作频率
（1）
SM7513 芯片开关频率由负载大小来控制，不需要外接频率设置元件（最大开关频率要小于 65K） 。在不连 续模式的反激电源中，最大输出功率为：
1 2 Po = × L P × FSW × IP 2
（3）
注：控制变压器漏感可省去吸收电路
注：如需最新资料或技术支持，请与我们联系
-4-
SM7513 恒流原边控制功率开关 v1.6
SM7513 10V/300mA LED 低端照明应用方案 原理图：
F1 DB1 Vout+ D1 E2 R2 Vout-
AC E1
1 CS 2 NC 3 EM DRAIN DRAIN GND 8 7 6
电气工作参数
(除非特殊说明，下列条件均为 TA=25℃，VCC=6V) 符号 ICC Vcc Vcs 说明 静态电流 内部供电电压 电流检测阈值 前沿消隐时间 最小消磁时间 最大占空比 导通电阻 抗击穿电压 Vcc 欠压保护阈值 最大消磁时间 范围 最小 典型 -250 6 620 450 5 42 30 730 4 150 最大 uA V mV nS uS 单位
管脚图
1 2 3
CS DRAIN
8 7 6 5
SM7513
NC EM
DRAIN GND GND
4 VCC
输出功率表
BP1360
BP136030V/500mA高调光比LED恒流驱动芯片首页--产品介绍BP3108--BP2808--BP2802--BP1360--BP1361--BP1601--BP8101--BP3102--BP3105--特点:应用:极少的外部元器件MR16/11 LED 射灯代替卤素灯很宽的输入电压范围：从5V 到30V 车载LED 灯±3%的输出电流精度LED 舞台灯LED 开路保护太阳能LED 灯LED 短路保护LED 信号灯最大输出600mA的电流LED 路灯复用DIM 引脚进行LED 模拟调光和PWM 调光高达97%的效率输出可调的恒流控制方法驱动芯片BP1360 是一款驱动高亮度LED 的降压恒流驱动芯片。
BP1360 外部采用极少的元器件，为MR16 LED灯杯、LED 舞台灯、车载LED 灯、太阳能LED 灯和LED 路灯提供一个极高性价比的解决方案。
BP1360输入电压范围从 5 伏到30 伏，输出电流通过采样电阻设定，单颗LED 最大输出电流可达600 毫安。
BP1360 采用专利技术的恒流控制方法使得LED 电流精度高达±3％。
BP1360 通过DIM 引脚接受0.5-2.5V 的模拟调光以及频率范围很宽的PWM 调光。
当DIM 的电压低于0.3V 时，功率开关关断，BP1360 进入极低工作电流的待机状态。
BP1360 内置功率开关，根据不同的输入电压，BP1360 可以驱动多颗1 瓦或单颗3 瓦的LED。
BP1360 包含过温保护、LED 短路和开路保护功能。
BP1360 采用体积很小SOT23-5 封装。
管脚封装管脚描述管脚号管脚名称描述1 SW 功率开关的漏端2 GND 信号和功率地3 DIM 开关使能、模拟和PWM调光端4 CS 电流采样端，采样电阻接在CS和VIN端之间5 VIN 电源输入端，必须就近接旁路电容定购信息定购型号封装温度范围包装形式打印BP1360ES5 SOT23-5 -40 o C到85 o C Tape and Reel 1360。
LED 手电筒驱动专用IC
xx135 **** ****
公司专业的角度为您提供优质的产品，让您用实惠的价格，购买到您需要的产品和优质的服务。
升压芯片，同步降压芯片，同步升压降压芯片，LED背光驱动IC,LED照明驱动IC,线性恒流IC,线性稳压LDO,锂电充电IC,锂电保护IC,电压检测IC等等是我们的主打产品。
同时我们提供专业的技术支持，让您能更快的设计生产产品，获得市场先机。
LED手电筒驱动专用IC特点：
工作电压：2V~6V
工作模式1:全亮、闪亮
工作模式2:全亮、暗亮、闪亮
最大LED电流：200mA
欠压保护：2V
LED手电筒驱动专用IC应用领域：
LED手电筒装
LY2210采用SOT23和TO92两种封装
LED矿灯、头灯
专门为LED手电筒、矿灯、头灯等设计的控制芯片。
LY2210支持一组LED 灯，灯的控制由开关来完成。
LY2210有两种工作模式：
在工作模式1下，LED灯可在"全亮"和"闪亮"这两种工作状态之间切换；在工作模式2下，LED灯可从"全亮"状态切换到亮度的"暗亮"状态再到"闪亮"状态，这三种工作状态是循环往复切换的。
LY2210最大工作电流为200m
A.
1/ 1。
QX7135中文规格书
芯片内部包括软启动电路、过温保护 电路、参考电压电路、欠压保护、LED 短 路保护电路以及功率管。
当输入电压较高时，或者输出电流较 大时，芯片上消耗的功耗较大，芯片会进 入过热保护状态，降低输出电流，可有效 保护芯片，避免结温超过 120oC 时因过热 而造成损坏。
QX7135 自带软启动功能，该功能可 以防止芯片在上电瞬间出现 LED 亮度的 闪烁。
QX7135 可通过多个并联的方式扩展 LED 的电流驱动能力，如图 3 所示：
QX7135 QX7135 QX7135
VIN DC
VDD
CIN
LED
GND
VDD LED
GND
IOUT=1.05A
VDD LED
GND
QX7135_DS02CN
7135 XXX
1
2
3
LED GND VDD
SOT-89-3
泉芯电子技术(深圳)有限公司
2 of 8
管脚定义
QX7135 线性降压 LED 恒流驱动器
管脚号 管脚名称 管脚类型
描述
1
LED
输出
LED 脚，接 LED 阴极
2
GND
输入
电源地
3
VDD
应用领域
线性 LED 照明驱动 LED 手电筒、LED 台灯、LED 矿灯、
LED 指示灯等
典型应用电路图
VIN DC
…
VDD
CIN
LED
QX7135
GND
QX7135_DS02CN
图 1：QX7135 典型应用电路图
离线式开关电源开关芯片SM8513 说明书
(4)
因为消磁时间 TDEMAG 和电感量成反比， 通过频率锁定， Lp 和 FSW 的乘积保持不变。
V1006A
第 6 页， 共 11 页
离线式开关电源开关芯片
SM8513
所以最大输出功率和恒流模式下的恒流电流不会随原边电感量变化。 SM8513 能最大补偿 电感量±10%的变化。 抖频 SM8513 采用了抖频技术。通过调制震荡频率，可以将噪音的能量频谱展开，达到减 小 EMI 的效果，并使系统设计更简单。 电流检测和 LEB SM8513 电流模式的 PWM 控制中提供了逐周期电流限制。开关电流通过外接的检测 电阻输入芯片限流脚 CS。芯片内部的前沿消隐电路将检测到的 MOS 导通瞬间的电压尖 峰忽略，因此在电流检测脚可不接 RC 滤波电路。电流检测脚的输入电压与误差放大器的 输出电压共同决定 PWM 占空比。 GATE 驱动 SM8513 内部采用一种专用驱动电路驱动功率 MOS 来进行功率开关控制。如果驱动 电路驱动能力太弱会增加 MOS 的开关损耗，而驱动电路驱动能力太强时，系统的 EMI 性能又会变差。 线损补偿 SM8513 通过内置线损补偿来实现优秀的负载调整。芯片 FB 输出电流经分压电阻产 生一个补偿电压，来实现负载补偿。由于 FB 电流和 COMP 脚电压成反比，因此 FB 电流 与输出负载电流成反比，从而使由于线压降而损失的输出电压得以补偿。当负载电流从 满载降到空载，FB 产生的补偿电压会逐渐升高。因此通过改变分压电路的电阻阻值，可 以补偿不同线损对输出电压的影响。 保护控制 SM8513 的保护功能提高了电源系统的可靠性， 包括： 逐周期电流限制 （OCP） ,VDD 嵌位，软启动和欠压锁定等。 芯片正常工作时，由变压器辅助线圈提供芯片 VDD 电压。当 VDD 降到低于 VDD 关闭电压时，系统没有输出，芯片进入重启过程。
AW2013DNR_七彩呼吸灯驱动产品手册
6.3 读写操作 ........................................................................... 8
6.3.1 写操作 .................................................................... 8
6.1 通讯协议 ........................................................................... 8
6.2 I2C 接口地址 ........................................................................8
2
LED1
LED 驱动口，外部通过 LED 连电池电压 VBAT
3
LED2
LED 驱动口，外部通过 LED 连电池电压 VBAT
4
INTN
中断，开漏输出，低有效。外部通过电阻上拉到高，不用时可 悬空。
5
VCC
电源电压，2.5-3.3V
6-8
NC
未使用，悬空
9
SDA
I2C 接口双向数据线，1.8V/3.3V 兼容
8.1 概述 .............................................................................. 10
8.2 LED 功能控制 ......................................................................11
6.5 中断 .............................................................................. 10
明微SM16703PB低压幻彩灯带灯条恒流驱动芯片产品说明书(1)
Current Module
Constant Current Driver R
OUTR
Constant Current Driver G
OUTG
Constant Current Driver B
OUTB
管脚说明
编号 1 2 3 4 5 6 7 8
GND Fig. SM16703PB 内部功能框图
名称 OUTR OUTG OUTB GND DOUT DIN
VDS_R=1V
-
16
-
mA
VIH 输入信号阈值电压
VIL
DIN 输入高电平 DIN 输入低电平
0.7xVDD
-
-
V
-
-
0.3× VDD V
IDOH
DOUT 输出电流
DOUT 端口短接地，最大驱动电流
-
45
-
mA
IDOL
DOUT 灌电流
DOUT 端口短接 VDD，最大灌电流
-
-45
VDS_S %VS.VDS
SM16703PB 装饰照明驱动 IC IBZIZOV1.1
SM16703PB
概述
SM16703PB是单线传输三通道LED驱动控制专用芯 片，采用单极性归零码通信协议。
SM16703PB内部包含电源钳位模块、信号解码模 块、振荡模块、数据再生模块、输出电流驱动模块等。 其中数据再生模块在接受完本芯片的数据后，自动将级 联输出的数据整形转发，保证数据串联传输过程中不衰 减。
电气工作参数（注 4、5）
若无特殊说明，VDD=5V，TA=25° C。
符号
参数
测试条件
最小值 典型值 最大值 单位
外部电源 VCC=12V，VCC 与 VDD 间的
AMC7135 350mA 恒流LED驱动电路总汇
简单介绍
AMC7135350mA恒流LED驱动ic方案汇总主要包含：1.基本典型应用。
2.防反接LED手电筒电路。
3.多颗AMC7135并联驱动700mA~1A应用。
4.高电压输入驱动多颗串接LED应用。
5.通过微控制器控制RGB 三色LED灯。
6.AMC7135主辅灯可切换的LED矿灯应用。
7.AMC713512V输入驱动三串多并LED应用。
AMC7135350mA恒流LED驱动ic方案汇总
概述AMC7135堪称一款经典的降压恒流驱动芯片。
平实的价格、简单的电路结构及稳定
的性能着实让它的使用者们津津乐道。
但是除了典型应用AMC7135还可以做更多的
事，简单的东西不简单就看大家怎么去发挥它了。
技术参数
350mA恒流输出（电流档位可选）
输出开短路保护
低压差
低静态电流
供电范围：2.7V~6V
2KV ESD
先进Bi-CMOS工艺
SOT89和TO252封装
AMC7135应用方案汇总见下（附电路图）
1.典型应用电路无需任何外围器件
2.防电池反接的LED驱动电路
3.多颗AMC7135并接驱动700mA~1A应用
4.输入12V驱动3颗串接白光LED应用（如负载改为红光LED VF=2V，该应用则可串5颗LED）
5.通过微控制器及on/off装置配合7135实现RGB三色LED亮暗程度的控制。
达到多彩混色的功
能。
6.矿灯所需的主灯及辅灯可切换照明电路
7.输入电压12V，采用78L05降压，配合7135实现1W LED3串多并电路
资料收集：冯教授。
PL3536_7-13x1W LED驱动电源方案
单位用量 1 1 1 1 1 2 1 1 1 2 1 4 2 1 0 1 1
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©PMICRO Electronics
PL3536 7-13x1W LED DEMO DRIVER
3、变压器
1 5 初级 次级 3 8
3 层绝缘胶带 辅助 0.31mm，20T 2 层绝缘胶带 次级 0.27mm，46T 2 层绝缘胶带
2 辅助 4
初级 0.21mm，73T
初级电感量 0.75mH@10kHz 磁芯：EE1916（PC40 或等效材质） 骨架：EE1916 卧式
©PMICRO Electronics
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PL3536 7-13x1W LED DEMO MICRO Electronics
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PL3536 7-13x1W LED DEMO DRIVER
5、输出 Vo-Io 曲线
60.00 50.00 输出电压（V） 40.00 30.00 20.00 10.00 0.00 0.000
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110Vac 220Vac
V-I曲线
0.050
0.100
0.150
0.200
0.250
0.300
0.350
输出电流（A）
©PMICRO Electronics
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PL3536 7-13x1W LED DEMO DRIVER
6、图片
©PMICRO Electronics
PL3536 7-13x1W LED 驱动器
概述： 1. 内部集成 MOSFET，设计简单； 2. 精确的原边恒流控制，无需 TL431 和光耦等反馈元件； 3. 芯片具有过压过流保护，输出短路开路保护等功能。
高精度LED原边恒流驱动PT4213
PT4213Primary Side CC ControllerGENERAL DESCRIPTIONThe PT4213 is a primary side regulated constant current controller, which is designed for LED lighting applications. The device regulates output current without the secondary feedback loop. The device integrates an oscillator, a current sense circuit, CC control circuit, a pre-driver and a complete set of protection circuits to protect against all fault conditions including output open/short circuit, line under-voltage, and over temperature protection. The PT4213 is available in SOT23-6 package.FEATURESCC Without Secondary Feedback Inductance Compensation Low Startup Current (<10uA) Adjustable Primary Side Current limit VCC/FB Over Voltage Protection VCC/FB UVLO Feedback Loop Open Circuit Protection Over Temperature Protection RoHS compliantAPPLICATIONSOff-line High Brightness General LED Lighting Integrated LED Lamps such as GU10, E27, PAR20/20/38 LED LampsORDERING INFORMATIONPACKAGESOT23-6， free PbTEMPERATURE RANGE-40℃ to 85℃ORDERING PART NUMBERPT4213E23FTRANSPORT MEDIA3000/Tape and ReelMARKING4213TYPICAL APPLICATION CIRCUITD2LED+C4AC IN 85～265VC1R2C2LEDR1 D1T1R5 R3D3Q1VCC FB GATE CSR6PT4213R4C3GNDChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 1PT4213Primary Side CC ControllerPIN ASSIGNMENTPIN DESCRIPTIONSPIN No. 1 2 3 4 5 6 PIN NAMES CS GND NC GATE VCC FB DESCRIPTION Primary Side Current Sense Input Ground Not connected Drive output Power supply, the device is supplied by an auxiliary winding. Auxiliary Winding Voltage Sense InputABSOLUTE MAXIMUM RATINGS (note1)SYM PARAMETER VALUE UNITVCC VFB VCS VGATE Topt Tstg ESDRΘJAVCC pin Voltage FB pin Input Voltage CS pin Voltage GATE pin output voltage Operating Junction Temp. Range Storage Temp. Range HBMSOT23-6-0.3~30 -0.3~5 -0.3~5 -0.3~15 -40 to 150 -55 to 150 2000250V V V V ℃ ℃ V℃/WNote 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Recommended Operating Range indicates conditions for which the device is functional, but do not guarantee specific performance limits. Electrical Characteristics state DC and AC electrical specifications under particular test conditions which guarantee specific performance limits. This assumes that the device is within the Operating Range. Specifications are not guaranteed for parameters where no limit is given, however, the typical value is a good indication of device performance.RECOMMENDED OPERATING RANGESYM PARAMETER VALUE UNITVCC TAVCC pin Operating Voltage Operating Ambient Temperature9.5~26 -20~85V ℃China Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 2PT4213Primary Side CC ControllerELECTRICAL CHARACTERISTICS(TA=25℃, VCC=16V，fsw=65KHz unless specified otherwise) SYMBOL PARAMETER TEST CONDITION MIN TYP MAX UNITSUPPLY VOLTAGE (VCC) ISTART VVCC_ON VVCC_OFF VVCC_Clamp VVCC_OVP IVCCQ Start up current VCC turn on threshold VCC minimum voltage operating VCC=12.0V VCC Rising VCC Falling Icc=10mA 26 No switching 12.5 7.5 1 14.0 8.5 33 27.5 350 29 700 10 15.5 9.5 uA V V V V uAVCC Clamp Voltage VCC Over Voltage Protection Threshold VCC Supply CurrentFEED BACK VOLTAGE SENSE PIN (FB) VFBMAX VFBMIN IFB_OPEN FB Over Voltage Protection FB Minimum Voltage FB Open Loop Current 2.4 2.5 0.8 -85 2.6 V V uACURRENT SENSE INPUT PIN (CS) VCS TLEB Current Limit Threshold Current sense Leading Edge Blanking Time Maximum driving pulse duty cycle Rising time Falling time Gate clamp voltage Cgate=1nF Cgate=1nF Ifb=0 490 500 250 510 mV nSDRIVE OUTPUT (GATE) Dmax Tr Tf VGS_MAX PROTECTION TSD Thermal Threshold Shut Down 150 ℃ 65 220 120 15 % nS nS VChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 3PT4213Primary Side CC ControllerSIMPLIFIED BLOCK DIAGRAMOPERATION DESCRIPTION The PT4213 consists of an oscillator, feedback circuit, over-temperature protection, frequency jittering, current limit circuit, leading-edge blanking, and constant current control circuitry. The switching frequency is modulated to regulate the output current to provide a constant current characteristic. It senses and regulates output current from primary side of transformer and is ideal for high precise, high reliability and cost effective LED lighting application. THEORY OF OPERATIONFigure 1 illustrates a simplified flyback converter. When the switch Q1 turns on, the voltage across the primary winding is Vbus. Assuming the voltage dropped across Q1 is zero, the current in Q1 ramps up linearly at a rate of Vbus/Lp. When the current in Q1 reaches a predefined value of Ipk_pri the controller forces Q1 turns off. During the Q1 on-time, the rectifying diode D2 is reverse biased and the load current Io is supplied by the secondary capacitor C4. When Q1 turns off, D2 conducts and the stored energy is delivered to the output. The PT4213 is designed to operate in discontinuous conduction mode (DCM), in DCM the energy stored in primary winding is transported to the secondary winding completely during each cycle. The output current is determined by Rcs and primary/secondary turns ratio of the transformer. Assuming the transformer primary/secondary turns ratio is Nps. The output current is given by following expression:China Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 4PT4213Primary Side CC ControllerI out = 0.1125 * N ps Rcssource terminal and GND and feeds to CS input. At each switching cycle when the voltage of CS input excess the internal threshold the driving signal is terminated after a short delay. The relationship between the CS threshold and the primary peak current passing through power MOSFET Q1 follows below expression: Ipk_pri=Vcs/Rcs; Ipk_pri is the peak current through power MOSFET, VCS is the voltage threshold of pin1 of PT4213 and Rcs represents sensing resistor. A spike is inevitable on the sensed signal on Rcs at the instance when the power MOSFET is turned on due to the recovery time of the secondary rectifier and the snubber circuit. The LEB has been implemented in PT4213, during the LEB time the current sense comparator is disabled so the switching signal can not be terminated by the turn-on spike on the sensed signal so the external RC filter can be removed.START UP Once the AC voltage is applied to the application circuit, the Vbus charges VCC pin up through the start up resistor R1, when the voltage on VCC pin reaches its VCC_ON threshold the controller starts to deliver the driving pulses to power switch Q1 and VCC is powered by auxiliary winding. Thanks to the very small start up current, a large start up resistor R1 could be used in the start up circuit to minimize power loss. For the applications with general 90-264Vac input range, a 1/8W resistor between 0.5Mohm and 3Mohm and a 4.7uF/50V capacitor C3 compose a simple and reliable start up circuit.CURRENT LIMIT COMPENSATION CONSTANT CURRENT (CC) OPERATION The PT4213 regulates output current from the primary side control. The switching frequency is adjusted as the feedback pin voltage increases to provide a constant output current regulation. PRIMARY INDUCTANCE COMPENSATION With the inductance compensation function output current is free of primary inductance variation. If the primary magnetizing inductance is either too high or low the converter will automatically adjust the Oscillation frequency to maintain the constant output current. CURRENT SENSE AND LEB The current of the power MOSFET is transferred to voltage signal through a resistor connected between The current limit circuit senses the current in the power MOSFET from the resistor connecting between the source of MOSFET and GND. The current sense resistor converts the current in the power MOSFET to voltage signal and then feeds to CS pin. When the voltage on CS pin exceeds the internal threshold VCS which is defied as 500mV, the power MOSFET is turned off for the remainder of that cycle. Excellent regulation performance is achieved with C.R.PowTech proprietary line regulation control technique. SHORT CIRCUIT PROTECTION In the event of a fault condition such as an output short condition the PT4213 enters into an appropriate protection mode as described below. In the event the feedback pin voltage falls below 0.8V during theChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 5PT4213Primary Side CC Controllerdischarged period of the inductance of the primary winding, the converter enters into short circuit protection mode after the feedback pin sampling delay for the duration in excess of ~30 ms, wherein the device is disabled. VCC will then drops due to internal power consumption. When VCC drops below the VVCC_OFF turn-off threshold, the PT4213 will be totally shut down and the start up sequence will kick in and VCC is charging up again. The device is alternately enables and disables until the fault condition is removed. OPEN CIRCUIT PROTECTION In the event of a fault condition of the output open circuit the PT4213 enters into an appropriate protection mode as described below. In the event the feedback pin voltage is over 2.5 V during the discharged period of the Lp (the inductance of the primary winding of the main transformer), the switching frequency is decreased and peak current is also decreased to 50%. If the over voltage condition duration time excess 8 consecutive cycles the controller is disabled. FREQUENCY JITTERING The frequency jittering is implemented in the PT4213. The oscillation frequency is modulated so that the tone energy is spread out. The spread spectrum minimizes the conduction band EMI and therefore reduces system design challenge. OVER TEMPERATURE PROTECTION The thermal shutdown circuitry senses the die temperature. When the die temperature is above 150°C the device is disabled and remains disable until the die temperature falls by 20°C. VCC OVER VOLTAGE PROTECTION VCC over voltage protection is designed to protect the device from damage of over voltage. When the voltage on VCC reaches the OVP threshold the PT4213 stops delivering PWM signal to the power MOSFET, voltage on VCC begins to drop due to the internal power consumption, the PT4213 will recover from OVP status when voltage on VCC drops below the OVP release threshold. GATE OUTPUT The output drives the GATE of the power MOSFET. The optimized totem-pole type driver offers a good tradeoff between driving ability and EMI. Additionally the output high level is clamped to 15V by an internal clamp so that power MOSFET transistor can be protected against undesirable gate over voltage. A resistor between GATE and GND initials the gate voltage to zero at the off state.China Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 6PT4213Primary Side CC ControllerTYPICAL PERFORMANCE CHARACTERISTICSDESIGN Example and Notes: A design example is given to illustrate how to design an Off-line AC/DC LED driver step by step based on PT4213. Refer to figure 4 for the application circuit. 1 Determine input and output The design spec is given in Table 1. It is intended to drive 5pcs 1W white LED in series for general lighting Table 1 Parameters Input Voltage Symbol Vin Limits 90-264VacFrequency Output Voltage Max Vout Min Vout Output Currentfline Vout Voutmax Voutmin Iout47-64Hz 16V 17.5V 15V 320mA2 Set the switching frequency The maximum operating frequency is limited by PT4213 sampling delay time on FB pin during the flyback period. To sample the voltage on FB pin correctly the secondary side discharge duration timeChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 7PT4213Primary Side CC Controllermust be more than 3.5uS, and the maximum limited switching frequency for PT4213 is 128 KHz. In practice, the suitable switching frequency for this design is set to 65KHz considering the EMI, efficiency and the size of the main transformer. For this design example, the switching frequency fsw and operating period Tsw is set as below: f sw = 65 KHz rectifying diode D3, the primary side inductance Lp, the primary peak current Ipk_pri, and the minimum operating input voltage Vin_dc_min. The smaller of Nps, the smaller of Vin_dc_min and less capacitance of the bulk capacitor is required. But it is led to higher reverse voltage for the secondary rectifying diode D3. In practice, the recommended Nps is less than 5.0 for general applications with 85VAC-265VAC input.Tsw = 1 / f sw = 15.4us3 The maximum duty cycle For PT4213, the discharged time tdis of the inductance of the primary winding is fixed to be 45% of the operating cycle. Keep in mind the operation of the LED driver using PT4213 should be DCM in the full input voltage range in order to regulate the LED current precisely. So: Tsw = ton + t dis + t dead ton: turn on time of the switch MOSFET Q1 tdis: discharge time of Lp tdead: dead time of the flyback DCM mode t dis = 0.45 * Tsw (2) (3) (1)Vin _ dc _ min * t on _ max = N ps * Vout * t disFrom equation (4), the below equation is given(4)N ps =Vin _ dc _ min * t on _ maxVout * t dis(5)For this design example, the minimum operating input voltage is estimated to be approximately 60Vdc as a start point.N ps =Vin _ dc _ min * t on _ maxVout * t dis= 60 * 5.3916 * 6.93= 2.925 Calculate the current sense resistor Once Nps is determined, the current sense resistor Rcs can be calculated from following expression:t dead _ min = 1.5 * 2π L p * CdsRcs =For this design example, the minimum tdead_min can be estimated to be approximately 20% of the switch cycle as a start point and then adjusted after the LED driver is made.0.1125 * N ps I out Vcs 0.5V = Rcs Rcs(6)I pk _ pri =(7)t dead _ min = 1.5 * 2π L p * Cds = 20% * Tsw = 3.08ust dis = 45% * Tsw = 6.93usFor this design example,R4 = Rcs =ton _ max = Tsw − t dis − t dead _ minDmax = ton _ max T sw = 35%0.1125 0.1125 * 2.92 = 1.0Ω * N ps = I out 0.32I pk _ pri =Vcs 0.5V 0.5V = = = 0.5 A Rcs Rcs 1.0Ω4 Turns Ratio The maximum allowable Nps is determined by the voltage stress on power switch Q1, the minimum operating voltage Vin_dc_min and primary side inductance Lp. The minimum allowable Nps is limited by the maximum allowable reverse voltage on the secondary rectifying diode D3. So the Nps is the trade-off among the Drain-Source breakdown voltage of the power switch Q1, the breakdown voltage of the secondary6 Calculate the primary inductance Primary inductance Lp is determined by the output power, the switch frequency fsw, the primary peak current Ipk_pri and the flyback converter efficiencyη . The relationship between primary energy and the secondary energy is given by:1 2 L p * I pk − pri * Fsw *η = Vout * I out 2(8)From the equation (8), the primary inductance Lp of theChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 8PT4213Primary Side CC Controllermain transformer can be derived: 2 * Vout * I out Lp = 2 I pk − pri * Fsw *η and Rfb_dn (9) For better regulation the current flowing out from FB pin of PT4213 at 220VAC input voltage is better to be approximate 1mA, so the Rfb_up is given by:For this design example, 2 * Vout * I out 2 * 16 * 0.32 Lp ≤ = = 0.7 mH 2 0.52 * 65 * 103 * 0.90 I pk − pri * Fsw *η For this design example, Lp is chosen to be 660uH. 7 Calculate the primary winding In order to keep the transformer from saturation, the maximum flux density must not be exceeded. So the minimum turns of the primary winding must meet: L p * I pk _ Pr i (10) Np = Ae *ΔBmax Where ΔBmax is the maximum allowed flux density and Ae is the core effective area. For this design example, EE16 core is selected. From the EE16 transformer core datasheet, Ae is 19.2,R fb _ up =2 * 220V N a * Np 1mA(13)Rfb_up unit is KΩ . For this design example,2 * 220V 17 * = 76.6 KΩ 1mA 69 R5 is chosen to be 75 KΩ for R5 for this design The low side feedback resistor is selected to set the R5 = R fb _ up =output OVP. Rfb_dn should be selected so that when output voltage reaches OVP, the voltage on FB pin reaches VFBMAX during transformer reset time. The relationship between Vovp and VFBMAX is:ΔBmax is chosen to be 2500 Gauss. So:Np = L p * I pk _ pri Ae *ΔBmax = 0.66 * 10 −3 * 0.5 = 68.75 19.2 *10 −6 * 0.25V FBMAX =R fb _ dn R fb _ up + R fb _ dnNa (Vovp + Vd ) (14) NsRe-arrange above expression Rfb_dn can be derived as:69 turns is chosen for this deign example. 8 Calculate the secondary winding The turns of the secondary winding can be calculated:R fb _ dn =V FBMAX * R fb _ up Na Ns(Vovp+ V d ) − V FBMAX(15)Ns =Np N ps(11)Vd: forward voltage drop of the secondary side rectifier diode, VFBMAX is maximum FB pin operating voltage which has a typical value of 2.5V. For this design example,For this design example,Ns =Np N ps=69 = 23.63 2.92R6 = R fb _ dn =2.5 * 75 = 14.82 KΩ . 17 (20 + 0.5) − 2.5 2323 turns is chosen for this design example. 9 Calculate the auxiliary winding The turns of the auxiliary winding can be calculated:R6 is chosen to be 15 KΩ ; output OVP is set to be 20V for this design example. 11 Select the secondary and auxiliary rectifying diode Maximum reverse voltage on secondary and auxiliary rectifying diode is: (12)Na =Vcc * Ns VoutIn practice Vcc is set to be 12V. For this design example,Na =Vcc 12 * N s = * 23 = 17.25 Vout 16Vsec_ diode ≥ (2 * 265 * N s + Vout ) Np(15)17 turns is chosen for this design example. 10 Determine feedback resistors Rfb_upChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 9PT4213Primary Side CC ControllerVaux _ diode ≥ ( 2 * 265 * N a + Vcc ) Npis filtered by the bulk capacitors C1 and C2. Inductor (16) L1, C1 and C2 form a pi (π) filter, which attenuates conducted differential-mode EMI noise. The secondary side of the transformer is rectified by D3, an ultra fast recovery diode and filtered by C5. The feedback resistors (R5 and R6) were selected using standard 1% resistor values for closed LED current. The feedback resistors should be placed directly at the FB pin of the PT4213 device to minimize noise. R1, R2 and C4 forms the start up circuit; the auxiliary winding is powered PT4213 through R7 and D2. C4 should be place as close as possible to the VCC and GND pins. R4 is the primary side current sense resistor, should be placed close to CS pin of PT4213.Peak current flowing in secondary rectifying diode is:I pk _ sec =0.5 * N ps Rcs(17)The secondary rectifying diode should be selected with the break down voltage higher than Vsec_diode and average forward current should be selected based on the output current and the secondary peak current. The auxiliary rectifying diode should be selected with the break down voltage higher than Vaux_diode. 12 PCB Layout The circuit shown in Figure 4 is configured as a primary-side regulated off-line flyback power supply utilizing PT4213 with 320mA CC output for driving 5pcs 1W LED in series. AC input power is rectified by BD1. The rectified DCChina Resources Powtech (shanghai) Co. LtdPT4213_DSB Rev EN1.0Page 10REFERENCE CIRCUIT FOR DRIVING 5X1W LEDFigure 4 PACKAGE INFORMATION (SOT23-6)尺寸（单位：毫米）尺寸（单位：英寸）符号最小值最大值最小值最大值A 0.787 1.450 0.031 0.057 A1 0.152 0.006B 1.397 1.803 0.055 0.071 b 0.250 0.559 0.010 0.022C 2.591 2.997 0.102 0.118D 2.692 3.099 0.106 0.122 e 0.838 1.041 0.033 0.041 H 0.080 0.254 0.003 0.010 L 0.300 0.610 0.012 0.024。
Infineon ICL5102 130W调光恒流LED驱动解决方案
解决方案
Universal AC and DC input Coreless transformer technology Input voltage range 85–305 V AC Integrated high-voltage gate driver Power factor > 99% Outstanding THD < 10% High efficiency up to 95% Short startup time < 300 ms 3 state self-adapting soft start Cap load regulation Start-up frequency up to 1.3 MHz Active burst mode less than 300 mW standby Stable low load operation mode Comprehensive protection mode with auto restart:Surge protection Output overvoltage Overcurrent Brown-in/brown-out Open loop Overtemperature using NTC -40°... +125℃
This supports stable operation even at low load conditions down to 0.1% of the nominal power without audible noise. The half-bridge resonant stage comes with integrated high- and low-side gate driver for discrete MOSFETs rated up to 650 V. Its non-overlap dead time is self adaptive from 500 ns ... 1.0 μs. A coreless transformer technology connects the high side stage. Fast time-to-light and low standby