LLC,300W,12V25A,97%效率

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产品知识100问

精心整理产品知识100问V1.0内容简介：本手册将产品销售中遇到的知识性问题整理成五个部分，即基本原理篇、技术标准篇、系统组件篇、疑难故障篇、产品应用篇，共100个问题，尽量做到通俗、全面。

本手册是互动开放式系统，我们会选择用户比较有代表性的问题，不断充实完善。

本手册仅供内部员工、代理商培训用，注意保密。

李庄2004-8-9电脑工号，再送220V高，1200uf6、开关电路的原理是什么？答：开关电路的原理是由开关管和PWM（PulseWidthModulation）控制芯片构成振荡电路，产生高频脉冲。

将高压整流滤波电路产生的高压直流电变成高频脉冲直流电，送到主变压器降压，变成低频脉冲直流电。

7、低压整流滤波电路的原理是什么？答：低频脉冲直流电经过二极管整流后，再由电解电容滤波，这样，输出的就是不同电压的稳定的电流了。

由于这里电压已经很低了，所以尽管电容容量很大，通常有1000uf、2200uf等，但由于不需要很高的耐压值，所以电容体积很小。

8、辅助电路有什么作用？答：300V直流电通过辅助电源开关管成为脉冲电流，通过辅助电源变压器输出二组交流电压，一路经整流、三端稳压器稳压，输出+5VSB，加到主板上作为待机电压；另一路经整流滤波，输出辅助20V电源，供给PWM等芯片工作。

有了辅助电路，计算机就可以实现软件开机、关机了。

9、什么是PFC？答：PFC（PowerFactorCorrection）即“功率因数校正”，主要用来表征电子产品对电能的利用效率。

功率因数越高，说明电能的利用效率越高。

通过CCC认证的电脑电源，都必须增加PFC电路。

位置在第二层滤波之后，全桥整流电路之前。

PFC有两种，一种是无源PFC于AT念。

个硬性的规定，禁止传导干扰过大的产品生产、销售。

14、电源测试中比较重要的有哪些项目？答：主要有交叉负载，浪涌，输入电压，纹波噪音，输出短路，过功率，转换效率，功率因数，响应时间，时序，噪音，传导辐射，漏电流，高低温测试等。

300W 24V

一、性能特点及适用范围LCAF220D24W300D-DF是我司设计生产的充电式模块电源，该电源具有体积小，转换效率高，性能稳定，原副边隔离，隔离强度高的优点；本产品采用金属外壳模块化封装，防尘防潮、抗干扰能力强；输入、输出端为接线端子形式便于连接；本产品电网适应能力强，可在较宽输入电压范围内工作；本产品具有输出短路、过压等保护功能。

另外，本产品具有智能充电功能，可对外接的24V电池充电,在交流断电时电池可不间断的对负载供电，具有防止电池过放电的保护功能；具有电源的状态显示；具有电池活化功能，手动或通过外部信号自动对电池进行活化维护。

本电源适用于电力配网自动化系统，电力智能箱变，环网柜以及其他行业需要不间断直流供电，要求较高的场合。

3.电源内部电路原理图1电源内部原理图图2电源内部隔离图4、面板说明图3电源面板说明1、充电及工作指示灯2、电池放电指示灯3、电池活化指示灯4、电池欠压指示灯5、电源故障（过压）指示灯6、手动活化启动按键7、手动活化退出按键8、手动电池投入按键9、手动电池退出按键1、接线端子5、接线说明5.1接线示意图图4接线示意图接线说明：K1K2K3为用户CPU等控制的继电器触点(触点容量无要求，但不可用光耦代替)，R为电池活化放电电阻，负载为用户正常负载，电池为24V电池组。

接线端子容量300V/15A。

具体使用见下面使用说明。

5.2端子定义端子号端子名称定义端子号端子名称定义1ACL交流输入L相12BG遥控电池退出2PE保护接地13RL活化放电负载正3ACN交流输入N相14VG遥控公共接点4NC无电气连接15Vo-负载输出负5VC告警输入正16Vo-负载输出负6POK输入失电告警输出17Vo+负载输出正7HOK电池活化状态输出18Vo+负载输出正8VL电池欠压告警输出19B+电池接入正9VH电源故障告警输出20B+电池接入正10HK遥控活化启动21B-电池接入负11HG遥控活化退出22B-电池接入负6、使用说明6.1电源状态指示充电，绿色，电池充电指示，电池充电时亮，电池放电或电池活化时熄灭；放电，红色，电池放电指示，电池放电时或电池活化时亮，电池充电及电池放电结束时熄灭；活化，黄色，电池活化时亮，否则熄灭；欠压，红色，电池或电源输出欠压时亮，否则熄灭；故障，红色，电源输出过压时亮，否则熄灭。

300w开关电源设计(图纸)

TND313/DRev 3, Sep-11High-Efficiency305 W ATX Reference Design Documentation Package© 2011 ON Semiconductor.Disclaimer: ON Semiconductor is providing this reference design documentation package “AS IS” and the recipient assumes all risk associated with the use and/or commercialization of this design package. No licenses to ON Semiconductor’s or any third party’s Intellectual Property is conveyed by the transfer of this documentation. This reference design documentation package is provided only to assist the customers in evaluation and feasibility assessment of the reference design. The design intent is to demonstrate that efficiencies beyond 80% are achievable cost effectively utilizing ON Semiconductor provided ICs and discrete components in conjunction with other inexpensive components. It is expected that users may make further refinements to meet specific performance goals.Table of Contents1.Overview (6)2.Specifications (7)3.Architecture Overview (8)4.Performance Results (13)5.Evaluation Guidelines (23)6.Schematics (24)7.Parts List (29)8.Critical Component Information (35)9.Resources/Contact Information (35)10.Appendix (36)List of TablesTable 1: Target Specifications (7)Table 2: Load matrix for efficiency measurements (13)Table 3: Load matrix for cross regulation measurements (15)Table 4: Transient load conditions (18)List of FiguresFigure 1: Reference Design Architecture Block Diagram (7)Figure 2: One switch forward topology and associated waveform (9)Figure 3: Active clamp forward topology and associated waveform (11)Figure 4: Efficiency vs percentage load from 20% to full load (13)Figure 5: Power factor vs percentage load (14)Figure 6: Efficiency vs percentage load from 5% to full load (14)Figure 7: 5 V and 5 V SBY outputs cross regulation vs load conditions (16)Figure 8: 3.3 V output cross regulation vs load conditions (16)Figure 9: 12 V1 and 12 V2 outputs cross regulation vs load conditions (17)Figure 10: -12 V output cross regulation vs load conditions (17)Figure 11: 5 V output transient load response (18)Figure 12: 12 V1 output transient load response (18)Figure 13: 12 V2 output transient load response (19)Figure 14: 3.3 V output transient load response (19)Figure 15: 5 V output voltage ripple at full load (20)Figure 16: 3.3 V output voltage ripple at full load (20)Figure 17: 12 V1 output voltage ripple at full load (20)Figure 18: 12 V2 output voltage ripple at full load (21)Figure 19: -12 V output voltage ripple at full load (21)Figure 20: 5 V SBY output voltage ripple at full load (21)Figure 21: Holdup time at full load (22)Figure 22: Input inrush current (22)Figure 23: ATX solution boards in ATX enclosure (24)Figure 24: PFC controller PCB board schematic (25)Figure 25: EMC component board (25)Figure 26: Active clamp controller PCB board schematic (26)Figure 27: Supervisory and 3.3 V post regulator controller PCB board schematic (27)Figure 28: Main PCB board schematic PFC and standby section (27)Figure 29: Main PCB board schematic active clamp stage section (28)Figure 30: Main PCB board schematic 3.3 V post regulator section (28)1. OverviewON Semiconductor was the first Semiconductor company to provide an 80 PLUS open reference design for an ATX Power Supply in 2005. This 1st generation reference design, was certified and met all the requirements of the 80 PLUS program. Following on this successful 1st generation design, ON Semiconductor is introducing its improved 2nd Generation reference design. This 2nd generation design utilizes newer ICs from ON Semiconductor that enable this design to exceed 80% efficiency starting at 20% load across different line conditions with ample margin to spare.This reference document provides the details behind this 2nd generation design. The design manual provides a detailed view of the performance achieved with this design in terms of efficiency, performance, thermals and other key parameters. In addition, a detailed list of the bill-of-materials (BOM) is also provided. ON Semiconductor will also be able to provide technical support to help our customers design and manufacture a similar ATX power supply customized to meet their specific requirements.The results achieved in this 2nd generation design were possible due to the use of advanced new components from ON Semiconductor. These new ICs not only speeded up the overall development cycle for this new design, but also helped achieve the high efficiencies while at the same time keeping a check on the overall cost. With the use of these new ICs, ON Semiconductor has proven again that the emerging requirements for high efficiency desktop power supplies can be met and further, can be optimized to meet specific performance vs. cost goals.This 2nd generation design consists of a single PCB designed to fit into the standard ATX enclosure along with a fan. Figure 1 below presents the overall architecture employed in this design – detailed schematics are included later in this design manual. As seen in figure 1, this design employed an Active Clamp forward topology using the new, highly integrated Active Clamp Controller IC from ON Semiconductor – NCP1562. A Continuous Conduction Mode (CCM) Power Factor Correction (PFC) IC was employed for the active PFC circuit. This IC, the NCP1653 provides an integrated, robust and cost-effective PFC solution. The standby controller, NCP1027, is an optimized IC for the ATX power supply and incorporates a high-voltage MOSFET. On the secondary side, this architecture employs a post regulator approach for generating the 3.3 V output. This is an alternative approach to the traditional magnetic amplifier (Mag Amp) approach. Though ON Semiconductor believes that this post regulator approach provides the highest efficiency amongst the different means of generating these outputs in the power supply, it is important to note that if the customer desires to use a different approach, that is possible – i.e. a similar design can be developed that utilizes all the other pieces of this architecture without the post regulator and still achieve very good results.With the introduction of this 2nd generation, high-efficiency ATX Power Supply, ON Semiconductor has shown that with judicious choice of design tradeoffs, optimum performance is achieved at minimum cost.Figure 1: Reference Design Architecture Block Diagram2. SpecificationsThe design closely follows the ATX12V version 2.2 power supply guidelines and specifications available from , unless otherwise noted. For instance, our reference design had a target of +/- 5% tolerance for both the 5 V and 5 Vstandby outputs. Further, the efficiency targets for the 80 PLUS program and the EPA’s Energy Star specification – Energy Star Program Requirements for Computers, version 4.0 that is set to take effect from July 20, 2007 – were targeted. Key specifications are included in Table 1 below.Output Current Tolerance (%) Ripple/Noise(mV) Min. (A) Max (A)5 V 0.3 22 ± 3.350 5 V standby 0.0 2.5 ± 3.350 12 V 1.0 18 ± 5.0120 - 12 V 0.0 1 ± 10120 Table 1: Target SpecificationsTarget specifications for other key parameters of the reference design include: -Efficiency: Minimum efficiency of 80% for 20%, 50% and 100% of rated output load conditions as defined by the 80 PLUS requirements as well as the Energy Star specification.-Power Factor: Power factor of 0.9 or greater at 100 % load.-Input Voltage: Universal Mains – 90 Vac to 265 Vac, 47 – 63 M Hz.-Output Power: Total maximum output power is 305 W.-Safety Features: As per the ATX12V specification, this design includes safety features such as OVP, UVP, and OCP.-This design meets the IEC1000-3-2 requirements over the input line range and under full load conditions.-This converter was designed for a 20 ms minimum Hold-up time.-Physical dimensions: This converter is designed to fit into the standard ATX enclosure with dimensions of 150 mm x 140 mm x 86 mm.3. Architecture OverviewBefore discussing the power supply architecture of the Generation 2 design, it is worth reiterating the design goals. We are tasked with providing a flexible power platform, which is required to have the lowest cost and highest efficiency that can be packaged in a small volume. The architecture must deliver a minimum of 80% efficiency over a wide range of operating conditions (high-line and low-line) as well as rated output load conditions (20% load and above). In addition we require a robust design solution having low parts count to provide the same performance on a unit to unit basis in a high volume manufacturing environment.The architecture selected follows a traditional two stage conversion approach as illustrated in Figure 1. It is worth noting that in order to achieve 80% efficiency overall, the efficiency of each of the two conversion stages must exceed 90 %. The front-end is a universal input, active power factor boost stage delivering a constant output voltage of 385 V to the active clamp stage. The second stage consists of two, dc-dc converters. The first down-stream converter processes 290 W required by the system in the form of tightly regulated +/-12 V, +5 V and +3.3 V outputs. The second converter delivers 15 W of standby power to another isolated 5 V rail.ON Semiconductor has developed multiple power management controllers and MOSFET devices in support of the ATX program. Web based data sheets, design tools and technical resources are available to assist design optimization. The ICs, supporting the ATX Generation 2 platform, are the NCP1653 PFC controller, the NCP1562 active clamp controller, the NCP4330 post regulator, the NCP1027 standby controller, and the NTP48xx family of MOSFET synchronous rectifiers. It is not possible to discuss the tradeoffs involved in each conversion stage at length, but the selection of the activeclamp forward converter topology is a key one and will be covered in depth. Each controller is highly integrated and offers the lowest external parts count available.PFC StageThere are a variety of PFC topologies available. These include discontinuous conduction mode (DCM), critical conduction mode (CRM) and continuous conduction mode (CCM). At this power level, CCM is the preferred choice and the NCP1653 will implement a IEC1000-3-2 compliant, fixed frequency, peak current mode PFC boost converter with very few external components.DC to DC (Main) ConverterThe selection of the dc-dc down stream converter is at the heart of the 80% solution. The traditional work horse of the ATX market has been the single switch forward converter operating at a switching frequency of 100 kHz. The converter and its associated drain waveform are illustrated in Figure 2. This topology is robust and delivers good full load efficiency performance at minimal cost. However, as power levels increase and regulatory requirements and energy conservation agencies drive for higher efficiency under all load conditions, the single switch forward topology in its simplest form is reaching its limit.Figure 2: One switch forward topology and associated waveformThere are several technical reasons for this. First, because the main transformer is reset via an auxiliary winding across the input bus, the duty cycle is limited below 50%. Second, because of this reset mechanism there is always a dead time interval, during each converter cycle, when no power is flowing. These two constraints have negative implications on the silicon utilization of the primary switch requiring a costly, large area die to be selected. The primary switch’s conduction loss is given by (1))(*2*)(on DS R P I D conduction loss P =(1)where, D is the duty cycle, I P is the primary current and R DS(on) is the switch on resistance. The topology is a hard switched topology with the primary switch being driven on with 385 V across it each switching cycle. The capacitive switch loss are given by (2),f DS V OSS C capacitive loss P *2*21)(= (2)where, C OSS is the switch output capacitance, V DS is the drain to source voltage and f is the operating frequency. Capacitive losses dominate at light load. Hence a switch selected for full load performance will suffer at light load because of its large drain source capacitance. Reviewing these two loss equations, it becomes apparent for efficiency enhancement under both full load and light load operation, a topology is required that allows the primary switch to operate at lower current and voltage stress. As the loss terms appear as current and voltage squared, small reductions in primary current I P and switch voltage V DS significantly improve performance.The active clamp forward converter illustrated in Figure 3 represents the ultimate extension of the single switch converter and provides these benefits. Instead of using an auxiliary winding, transformer reset is achieved using a clamp capacitor and an auxiliary switch. The reset period, controlled by the auxiliary switch now extends to the interval ()S T D *1−, completely eliminating the previous dead time interval. To maintain flux balance in the main transformer core, the reset voltage across the clamp capacitor isdetermined by the expression ()D D in V −1*. The duty cycle D of the single switch forwardconverter can extend beyond 50%, limited only by the primary switch’s maximum voltage rating.Figure 3: Active clamp forward topology and associated waveformFor a given set of conditions and power throughput, operating at extended duty cycles allows for a lower primary current. This in turn allows the selection of a smaller, lower cost die. Let’s look at a design example to illustrate this point.To reduce cost, a 150 μF bulk capacitor (instead of a 470 μF conventional value) is selected to provide 20 ms of hold up time. Using the energy storage equation given by (3),()ηtime up Hold Delivered Power V V C Energy f i **2122=−= (3)where, V i and V f are the initial and final voltages of the input capacitor, respectively. The initial voltage is 385 V and converter efficiency is 90%, allows us to calculate the final voltage V f to be 250 V. In the case of a conventional single switch design, the maximum duty cycle we can practically select and avoid transformer saturation is 0.45. The switch voltage stress is 2 x 250 V. With the active clamp single switch forward, the duty cycle can be extended to 0.67 and the voltage stress on the switch is Vin / (1-D) or 3.03 x 250 V. Each converter has to process 290 / 0.9 or 322 W from the primary bulk source. At nominal 385 V bulk, the average primary current is 0.84 A. Factoring in the primary switch duty cycle D, the peak current I P in the traditional forward converter is 0.65 / 0.45 or 1.44 times larger than the active clamp approach. Based on the conduction loss equation given by (1), we see that the 1.44 ratio holds true for conduction loss in the primary switch. Put another way, we can choose a MOSFET with 44% higher R DS(on) in the active clamp topology and have the same conduction loss. This is significant, as we can achieve better silicon utilization, lower cost and lower drain capacitance. By reviewing the data sheets from high voltage MOSFET vendors, it is possible to compare output capacitance C OSS versus R DS(on) as a function of die size. For example as MOSFET resistance increases from 3.6 Ω to 4.8 Ω, the output capacitance reduces from100 pF to 70 pF. The resonant nature of the active clamp allows the switch be turned on at 300 V instead of the conventional 400 V. These two effects allow a reduction in capacitive switching loss of 39% over a conventional design. Again, a significant improvement remembering that light load efficiency is determined predominately by switching loss. The example above illustrates how small changes in switch stress can impact overall cost and performance.The same argument relating to increased duty cycle operation extends to the secondary by proportionally reducing output rectifier loss. Since the secondary loss is a dominant factor at full load, an additional efficiency improvement/ cost benefit is realized. To achieve the ultimate efficiency, synchronous rectification is required on the +12 V and +5 V outputs. The single switch active clamp forward is very suitable to drive synchronous rectifiers directly from the secondary windings without the need for expensive gate drivers or additional delay timing circuitry.To allow designers to capitalize on the benefits inherent in the active clamp topology, the NCP1562 has been developed to capture all the necessary control features within a 16 pin package. The full featured controller has been designed for tight tolerance on all parameters, including the maximum duty cycle limit and the important soft stop function. To boost efficiency and maintain tight regulation, instead of the conventional magnetic amplifier post regulated approach, the 3.3 V output is derived from the 5 Volt winding of the main transformer. The MOSFET drivers, timing, synchronization and control functions to support this output are provided by the NCP4330 controller. A 6 W improvement in the loss budget is achieved when this approach is adopted. Gate charge and R DS(on) have been optimized in the NTP48xx family of MOSFETs and provide synchronous rectification for both the 3.3 V and 5 V outputs.Standby PowerThe NCP1027 integrates a fixed frequency current mode controller and a 700 volt MOSFET. The NCP1027 is an ideal part to implement a flyback topology delivering 15 W to an isolated 5 V output. At light loads the IC will operate in skip cycle mode, thereby reducing its switching losses and delivering high efficiency throughout the load range.4. Performance ResultsThe evaluation of the reference design focused on several areas including efficiency, power factor, cross regulation and transient load response. Design optimizations may be needed to customize this reference design to meet specific requirements.The converter efficiency is measured according to the operating conditions detailed in Table 2. The converter efficiency is measured at 100 Vac, 115 Vac and 230 Vac at 50 Hz. The converter achieves over 80% efficiency with room to spare over all load conditions as shown in Figure 4. The output voltages used for the efficiency calculations are measured at the end of the power cables. The fan is disabled for measurements at or below 20% load. The fan is automatically enabled once the load exceeds 60 W or 20%. The fan is operational for 50% and 100% load measurements. Further increases in the efficiency can be obtained for 50% and 100% load conditions through fan speed control.Load Condition Output Current (A) 5 V 3.3 V 12 V1 12 V2 -12V5 V SBY 5 % 0.690 0.540 0.385 0.385 0.030 0.070 10 % 1.390 1.070 0.770 0.770 0.070 1.390 15 % 2.080 1.610 1.150 1.150 0.100 0.210 20 % 2.7802.150 1.510 1.510 0.140 0.280 50 % 6.950 5.3703.845 3.845 0.350 0.700 100 %13.900 10.7407.695 7.6950.700 1.400Figure 4: Efficiency vs percentage load from 20% to full loadThe power factor exceeds 0.9 over all operating conditions as shown in Figure 5.Figure 5: Power factor vs percentage loadIn Figure 6, the efficiency measurements are shown from 5% load to full-load. Note that neither the 80 PLUS program nor the Energy Star specification require efficiencies above 80% for any output load below 20%. However, as can be seen in Figure 6, this reference design achieved 80% efficiency down to 16 % load.Figure 6: Efficiency vs percentage load from 5% to full loadOutput voltage cross regulation is measured according to the load conditions listed in Table 3. The results of the cross regulation measurements are shown inFigure 7 through Figure 10. Included in these figures are the tolerance requirements based on the target specifications listed in Table 1. The margin for the 5 V and 5 V SBY outputs can be increased by shifting up the regulation target for the 5 V outputs. It can also be improved by changing the weight of the 12 V and 5 V outputs in the regulation circuit.Load ConditionOutput Current (A)5 V(+/-3.3%)3.3 V(+/-4%)12 V1(+/-5%)12 V2(+/-5%)-12 V(+/-10%)5 V SBY(+/-3.3%)1 0.3 0.3 0 0 0 02 73 2 2 0.1 0.53 0.3 0.3 0 0 0 0.54 0.3 3 2 2 0.1 0.55 7 0.3 2 2 0.1 0.56 4 0.3 1 1 0.2 0.27 18 12 5 5 1 2.58 18 12 1 1 0.2 2.59 4 12 5 5 1 2.510 18 0.3 5 5 1 2.511 4 0.2 1 1 0.2 0.212 14 17 8 6 1 2.513 18 17 1 1 0.2 2.514 4 17 8 6 1 2.515 18 0.3 8 6 1 2.516 4 2 5 5 0.2 117 22 17 5 5 1 2.518 4 17 5 5 1 2.519 22 2 5 5 1 2.5Table 3: Load matrix for cross regulation measurementsFigure 7: 5 V and 5 V SBY outputs cross regulation vs load conditionsFigure 8: 3.3 V output cross regulation vs load conditionsFigure 9: 12 V1 and 12 V2 outputs cross regulation vs load conditionsFigure 10: -12 V output cross regulation vs load conditionsThe 5 V, 12 V and 3.3 V outputs are evaluated independently under transient load conditions. Each output is loaded at 50% and the load is reduced to 25% or increased to 75% of the maximum rated current. The transient voltage tolerance of each of the 5 V, 12 V and 3.3 V outputs is +/- 5%. Table 4 summarizes the transient load conditions and limits for each output. Transient waveforms are shown in Figure 11 through Figure 14.Output Minimum Load (A)Nominal Load (A)Maximum Load (A)Voltage under/overshoot (V) 5 V 5.5 11 16.5 ±250mV, ≤0.5V pk-pk 3.3 V 4.25 8.5 12.75 ±170mV, ≤0.34V pk-pk 12 V1 4.5 9 13.5 ±600mV, ≤1.2V pk-pk 12 V24.5913.5±600mV, ≤1.2V pk-pkTable 4: Transient load conditionsFigure 11: 5 V output transient load responseFigure 12: 12 V1 output transient load responseΔI LOAD = 11.5 A to 5.5 AΔI LOAD = 11.5 A to 16.5 AΔI LOAD = 9 A to 4.5 AΔI LOAD = 9 A to 13.5 AFigure 13: 12 V2 output transient load responseFigure 14: 3.3 V output transient load responseAll the outputs meet the transient voltage requirements under the evaluated conditions. The ripple voltage of each output is measured at the maximum load for each output. The output ripple is measured across 10 μF/MLC parallel 1000 μF low ESR/ESL termination capacitors. The target ripple is +/- 120 mV for the 12 V outputs and 50 mV for all other outputs. Figure 15 through Figure 20 show the output voltage ripple measurements. All outputs meet the voltage ripple requirements.ΔI LOAD = 9 A to 4.5 AΔI LOAD = 9 A to 13.5 AΔI LOAD = 8.5 A to 4.25 AΔI LOAD = 8.5 A to 12.75 AFigure 15: 5 V output voltage ripple at full loadFigure 16: 3.3 V output voltage ripple at full loadFigure 17: 12 V1 output voltage ripple at full loadFigure 18: 12 V2 output voltage ripple at full loadFigure 19: -12 V output voltage ripple at full loadFigure 20: 5 V SBY output voltage ripple at full loadThe required holdup time at full load is 20 ms. Holdup time is measured from the moment the AC power is removed to when the PWR_OK signal goes low. Figure 21 shows the holdup time at full load. Channel 1 is the AC power and Channel 2 is the PWR_OK signal. Holdup time is measured at 22.5 ms.Figure 21: Holdup time at full loadThe input inrush current of the system at 230 Vac at full load is measured at 28.8 A as shown in Figure 22.Figure 22: Input inrush current5. Evaluation GuidelinesEvaluation of the reference design should be attempted only by persons who are intimately familiar with power conversion circuitry. Lethal mains referenced voltages and high dc voltages are present within the primary section of the ATX circuitry. All testing should be done using a mains high-isolation transformer to power the demonstration unit so that appropriate test equipment probing will not affect or potentially damage the test equipment or the ATX circuitry. The evaluation engineer should also avoid connecting the ground terminal of oscilloscope probes or other test probes to floating or switching nodes (e.g. the source of the active clamp MOSFET). It is not recommended to touch heat sinks, on which primary active components are mounted, to avoid the possibility of receiving RF burns or shocks. High impedance, low capacitance test probes should be used where appropriate for minimal interaction with the circuits under investigation. Particular care should be taken when probing the high impedance input pins of the NCP1653 power factor controller and the NCP1562 active clamp controller. As with all sensitive switchmode circuitry, the power supply under test should be switched off from the ac mains whenever the test probes are connected and/or disconnected.The 3.3 V output does not have a minimum load requirement and a preload resistor is included in the -12 V output.The NCP1027 standby flyback converter will be operational as long as there is ac mains voltage applied to the system. This auxiliary converter can be evaluated by merely applying the mains voltage to the board. The supervisory IC enable input and monitoring circuitry will have to be disabled. The supervisory circuitry will normally cause a shutdown of the PFC (and the main converter) if the 3.3 V, the 5 V and the 12 V outputs are not sensed at their nominal voltage.The evaluating engineer should also be aware of the idiosyncrasies of constant current type electronic loads when powering up the ATX demonstration unit. If the loads are adjusted to be close to the ATX’s maximum rated output power, the unit could shut down at turn on due to the instantaneous overloading effect of the constant current loads. As a consequence, electronic loads should be set to constant resistance mode or rheostats should be used for loads. The other alternative is to start the supply at light to medium load and then increase the constant current electronic loads to the desired level.The board is designed to fit in a traditional ATX enclosure as shown in Figure23.Figure 23: ATX solution boards in ATX enclosure6. SchematicsThe power supply is implemented using a single sided PCB board. Added flexibility is provided by using daughter cards for the PFC (NCP1653), active clamp (NCP1562) controllers. A PCB board is also used for the 3.3 V post regulator (NCP4330) and supervisory controllers. This allows the use of newer generation controllers without the need of a complete re-layout of the main board. An additional daughter card is used for EMC components. The individual PCB board schematics are shown in Figure 24 through Figure 27.The schematic of the main PCB board is divided in three sections: PFC & standby section, active clamp section, and the post regulator section as shown in Figure 28 through Figure 30, respectively.Figure 24: PFC controller PCB board schematicFigure 25: EMC component boardFigure 27: Supervisory and 3.3 V post regulator controller PCB board schematicFigure 28: Main PCB board schematic PFC and standby sectionFigure 29: Main PCB board schematic active clamp stage sectionFigure 30: Main PCB board schematic 3.3 V post regulator section7. Parts ListThe bill of materials (BOM) for the design is provided in this section. To reflect theschematics shown in the previous section, the BOM have also been broken into differentsections and provided in separate tables – Table 5 through Table 9.It should be noted that a number of components used during the development cycle werebased on availability. As a result, further cost reductions and better inventorymanagement can be achieved by component standardization. IE, the unique part numberscan be SIGNIFICANTLY reduced by standardization and re-use of component valuesand case sizes. This will result in a lower cost BOM and better inventory management.Description Part Numbers Qty 0.1µF, ±10%, 500V, X7R, Case Size 1812 VJ1812Y104KXEAT 3 0.1µF, ±10%, 50V, X7R, Case Size1206 B37872K5104K060 18 0.1µF, ±20%,300VAC, Interference Suppression CapX2 PHE840EB6100MB05R17 2 0.22uF, ±20% ,300VAC, Interference Suppression CapX2 PHE840EX6220MB06R17 1 270µF, ±20%, 400V, -40°C to +85°C, B43501 series , Snap-In, Pitch 10mm B43501A9277M000 1 100pF, ±10%, 1kVDC,High voltage ceramic disc Capacitor, -25°C to +85°C DEBB33A101KC1B 2 100pF, ±5%, 50V, COG, Case Size1206 B37871K5101J060 1 1nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch MMK5 102M100J01L4 BULK 2 1nF, ±10%, 1kVDC,High voltage ceramic disc Capacitor,-25°C to +85°C DEBB33A102KA2B 2 1nF, ±20%,, 440VAC,Interference Suppression CapY1 PME294RB4100MR30 2 1nF,±20%, ,440/250VAC,Interference Suppression CapX1/Y2 2252 812 35 027 1 1nF, ±10%, 100V, COG, Case Size1206 B37871K1102J560 5 4.7nF, ±10%, 1kVDC, High voltage ceramic disc Capacitor, -25°C to +85°C DEBB33A472KA3B 1 4.7nF,±10% ,440/250VAC,Interference Suppression CapX1/Y2 2252 812 35 427 1 10nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch MMK5 103M100J01L4 BULK 1 10nF, ±10%, 50V, X7R, Case Size1206 B37872K5103K060 1 22nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch MMK5 223M100J01L4 BULK 1 2n2F, ±5%, 50V, COG, Case Size1206 B37871K5222J060 1 470pF, ±5%, 50V, COG, Case Size1206 B37871K5471J060 1 10µF, ±20%, 16V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free UVR1C100MDD 4 220µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 3.5mm, Pb Free UVR1E221MPD 1 3300µF, ±20%, 10V,-40°C to +85°C, Type VR, Radial, Pitch 5mm, Pb Free UVR1A332MHD 1 47µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free UVR1E470MDD 1 2200µF, ±20%, 10V,-40°C to +85°C, Type PM, Radial, Pitch 5mm, Pb Free UPM1A222MHD 2 220µF, ±20%, 25V,-40°C to +85°C, Type PW, Radial, Pitch 3.5mm, Pb Free UPW1E221MPD 2 470E, ±1%, 0.25W, Case Size 1206 MCR18 EZH F-4700 1 0.2E, ±1%,1W, Case Size 2010 CRL1206-FW-0R20E_ 3 0E022, ±5%, 3W,Wire Wound Resister BSI680E022±5%±100ppm/°C 1 100E, ±1%, 0.25W, Case Size 1206 MCR18 EZH F-1000 1 100E, ±1%, 0.25W, MFR EROS2CHF1000 2 10E0, ±1%, 0.25W, Case Size 1206 MCR18 EZH F-10R0 2 10E, ±1%, 0.5W, Case Size 2010 MCR50-JZH-J 10R0 5。

CM6901中文

Ns1 := Npmin Nratio1
Ns1 = 3.023
二次側繞組
Vin_nor
Nratio2 :=
Topology ⋅Trnum
(Vout2 + Vmosfet)⋅1.15
Nratio2 = 14.223
Ns2 := Npmin Nratio2
Ns2 = 3.023
二次側繞組
Bmax:=
⎛⎜ ⎜
10 Vs5 ( Fsw ) Vs6 ( Fsw )
5
2 .10 4
4 .10 4
6 .10 4
Fr Fmin>=Fr
8 .10 4
1 .10 5
1.2 .10 5
Fsw Switch Frequency
1.4 .10 5
1.6 .10 5
1.8 .10 5
Fmax
2 .10 5
圖一 SRC 負載曲線圖
SRC V.S LLC
用於直流輸出之共振式轉換器主要以串聯共振(Series resonant)為主架構，主要分成兩種負載曲線的操作區域，SRC 操作在共振點之上(操作在電感性負載區)， LLC 操作在共振點之下與第二共振點之間(操作在電容性負載區間)，以圖一 SRC；圖二 LLC 為負載曲線圖來做說明。
Design specifications.
k ≡ 103
m ≡ 10− 3
Input Specifecation
μ ≡ 10− 6
n ≡ 10− 9
p ≡ 10− 12
Vin_max:= 400
Output Specifecation
Vin_min:= 330
Vin_nor := 395
Vout1 := 12

300w开关电源方案

300W开关电源方案简介本文档介绍了一个300W的开关电源方案，用于提供稳定可靠的电源供应。

开关电源是一种将交流电转换为直流电的电源，通过开关管的开关动作来实现电压和电流的转换。

本方案采用了先进的电路设计和高效的开关管，以提高电源效率和稳定性。

方案设计输入电路300W开关电源的输入电压范围通常为220VAC或110VAC，本方案针对220VAC设计。

输入电路主要由滤波器、整流器和变压器组成。

滤波器用于滤除输入电压中的高频噪声，以保证输出电压的稳定性。

常见的滤波器电路包括Pi型滤波器和L型滤波器。

整流器将交流电转换为直流电，常见的整流器电路有全波整流和半波整流。

全波整流器可以实现较高的转换效率。

变压器用于将输入电压变换为适合开关电源工作的低压电压。

变压器一般由高频变压器和输出电感器组成，以提供高效的功率转换。

控制电路开关电源的控制电路主要包括开关管驱动电路和反馈控制电路。

开关管驱动电路负责控制开关管的开关动作，并控制输出电压。

常见的开关电源控制电路有固定频率PWM控制和变频控制。

反馈控制电路用于监测输出电压并调整开关管的开关动作，以稳定输出电压。

反馈控制电路一般由比较器、误差放大器和反馈元件组成。

输出电路输出电路主要由输出电感器、输出电容和负载组成。

输出电感器用于平滑输出电流，防止电流突变。

输出电容则用于平滑输出电压，提供稳定的负载。

负载是指连接在开关电源输出端的设备或电路，可以是各种电子设备、通信设备或其他电子装置。

负载的功率需小于或等于300W。

优点与特点高效率300W开关电源采用了高效率的开关管和控制电路，以减少功耗并提高转换效率。

高效率意味着更少的能量损耗，更低的温度和更长的使用寿命。

稳定性本方案采用了反馈控制电路来稳定输出电压，同时使用优质的电子元件和合理的电路布局，以提供稳定可靠的电源供应。

稳定的输出电压对各种设备和电路的正常运行至关重要。

可靠性300W开关电源采用了与国际标准相符的设计和制造工艺，确保产品的质量和可靠性。

300W AC DC 电源模块说明书

300W,165-264V AC Input,Dual outputAC/DC battery charging module power supplyRoHSFEATURES●Specially designed for Distribution Automation terminal design,suitable for 220Vdc operating mechanism,and it can charge for capacitor of 50000uF/250V ●Maximum instantaneous power up to 340W●With charging function,the 24V (6-30AH)output Lead-acid battery can be charged,when system connected with battery,it can be used as uninterrupted power supply●Designed in accordance with the power-related requirements of the State Grid Corporation,the main technical indicators meet the relevant industry standards●Battery reverse polarity protection,battery under voltage protection●Output over-current,over-voltage protection ●2.5KVAC high isolation voltage●Industrial grade operating temperature:-40℃to +70℃●Chassis mountingMBP300-2A27D27220is AC/DC battery charge power converter offered by Mornsun.It features wide input voltage range,taking both DC and AC input voltage,output over-current,over-voltage protection,strong ability in adapting power grid.This product has power working status display and Intelligent charging function,it can used to charge the 24V lead-acid battery,when AC is power-off,the battery can supply power to the load;it has battery over discharge protection function,Designed specifically for distribution automation terminal (DTU /FTU).It is widely used in the power industry switch substations,power substation,RMU,Intelligent Package Substation,Intelligent Switch Controller and other industries which need uninterrupted power supply.Selection GuidePart No.Output PowerNominal Output Voltage and Current Maximum Output PowerEfficiency(220VAC,%)(Vo1/Io1)(VB/IB)(Vo2/Io2)MBP300-2A27D2722062.5W27V/1.0A27V/0.5A220V/0.1A340W(No more than 20s,5mins once )80(Io1=1A,Io2=0.1A,disconnect the battery)Input SpecificationsItemOperating Conditions Min.Typ.Max.Unit Input Voltage Range AC input 165220264V AC DC input200310370VDC Input Frequency 475063Hz Input Current 220V AC,Typical load -- 1.0--AHot PlugUnavailableOutput SpecificationsItemOperating Conditions Min.Typ.Max.UnitRated Output CurrentInput voltage range Io1--1--A Io2--0.1--Peak Output Current *Input voltage range Io1(No more than 20s,5mins once,Io2≤0.1A)----6Io2(No more than 20s,5mins once,Io1≤1A)---- 1.36Output Voltage Input voltage range Vo1(Disconnect the battery)--27--VDC Vo2(Adjustable)200220240Line RegulationFull loadVo1--±0.5--%Vo2--±1--Load Regulation0%-100%load Vo1--±1--% Vo2--±5--Ripple&Noise**20MHz bandwidth(peak-to-peak value)(Io1=1A,Io2=0.1A,disconnect the battery)Vo1--200300mVVo2--2000--Floating Charge Voltage Room temperature,Io1=1A,Io2=0AVB--27--VDCBattery Charge Current Room temperature,Io1=1A,Io2=0AIB--0.5--A Battery Discharge Cut-off point Typical load Vo120.52121.5VDC Battery Discharge Cut-off Delay Time Typical load--3--sBattery Reverse Polarity Protection The green and the red lights are turn off,when the battery has been connected.Short Circuit Protection Input voltage range,disconnect the battery Hiccup,Continuous,self-recovery Over-current Protection Input voltage range,disconnect the battery Io1--16--A Over-voltage Protection Input voltage range,disconnect the battery----34VDC Hold-up Time Room temperature,220V AC input,Po=20W--0.3--s Note:*①When the ambient temperature exceeds50℃,Io1and Io2single peak current continuous output time can not exceed15s；②Io1and Io2can not simultaneously output peak current,product peak output power should not be more than340W.(Battery charging power included) **Ripple and noise are measured by“parallel cable”method,please see AC-DC Converter Application Notes for specific operationGeneral SpecificationsItem Operating Conditions Min.Typ.Max.UnitIsolation Voltage Input-outputTest time:1min,leakage current setting value:5mA2500----VAC Input-case2500----Output-case2500----Output-output1500----Impulse Voltage Input-output Apply5kV impulse test voltage between input andoutput.Add1.2/50us impact waveform,includingthree positive impulse and three negative impulsewhose time interval is no less than5seconds.And thereshould not have disruptive discharge during the test.5000----V Input-case5000----Output-case5000----Isolation Resistance Input-output Room temperature50----MΩInput-case Room temperature50----Output-case Room temperature50----Operating Temperature*-40--+70℃Storage Temperature-40--+85Shell Operation temperature*----+80Storage Humidity----95%RH MTBF MIL-HDBK-217F@25℃＞100,000hNote:*①When the ambient temperature exceeds50℃,it should be taken the cooling method of force air cooling or post cooling to ensure that the module shield temperature is not more than80℃.②When the ambient temperature is lower than-10℃,the product should be operated with rated load for1mins,before it output340W peak power. Physical SpecificationsCasing Material MetalPackage Dimensions200.00*102.00*45.00mmWeight850g(Typ.)Cooling method Free air convectionEMC SpecificationsEMS ESD IEC/EN61000-4-2Contact ±8KV Perf.Criteria B RS IEC/EN61000-4-330V/m perf.Criteria A EFT IEC/EN61000-4-4±4KV perf.Criteria B Surge IEC/EN61000-4-5line to line±2KV/line to ground±4KV perf.Criteria B CS IEC/EN61000-4-610Vr.m.s perf.Criteria A Voltage dips,short interruptionsand voltage variations immunityIEC/EN61000-4-110%,70%perf.Criteria BPrinciple block diagramFig1.Internal principle diagram Wiring Description1.Wiring diagram2.Terminal DefinitionTerminal No.Terminal name Definition1AC(L)AC input L phase2Protective grounding3AC(N)AC input N phase4-Vo1(B-)Control unit(-)Battery input(-)5B+Battery input(+)6+Vo1Control unit(+)7NC No electrical connection 8+Vo2Operating mechanism(+) 9-Vo2Operating mechanism(-) 10NC No electrical connectionManual Instruction1.Power supply status indicatorCharge,AC input power,green light on,the battery is in charging or floating charging status.Discharge,AC input power off,green light off,red light on,the battery is in discharging status.Reverse,when the input voltage off(or input voltage normal,Vo1and Vo2output normal),but the green and red light are all off,which shows that the battery is polarity reversed.Please check the wiring diagram to re-connect the battery.Input voltage(V AC)Output voltage(VDC)Whether to connectthe batteryLEDPower state Vo1Vo2green light Red light22027220no connect on off Output normal220Batteryvoltage220connect on off Output normal,battery charging000no connect off off No output000connect off on No output,battery access to normal220→0Batteryvoltage220connect on→off off→onOutput normal,battery from charginginto the discharge000connect off off No output,reverse connection ofbattery22027220connect off off Output normal,reverse connection ofbatterye of PowerThe power supply can work when input is AC the alternating current.The power input current to load is powered by power supply, meanwhile charge battery in constant current and voltage.After the battery is charged,power supply to floating charge state automatically,this moment,the power supply float voltage and current to normal self discharge of battery.When AC input voltage off,the battery will continue to power for load,0switch time.When the battery output voltage is lower than the under voltage protection point and last for3-10S，the power supply will turn off automatically.Without AC input,pass external passive nodes make Vo1and B+in short circuit(short circuit time:1-2S,but pin should not be short for a long time,otherwise the battery will lose the protection function.)that can enable the battery to start the output.Vo2output Voltage:200Vdc–240Vdc continuously adjustable,The user can adjust the output voltage to the knob with“output voltage adjustment”.e of BatteryThe power supply can be equipped with24V,6-30AH lead acid battery or colloidal maintenance-free battery,The battery is connected to the battery terminal(B+、B-)of the power supply.We should make sure that the input voltage is off before connect or disconnect the battery.If the red light on after connected the battery,the battery connected normal;if the red light off when connected the battery,the battery polarity connected reverse,please check the wiring diagram to re-connect it.It is forbidden to short-circuit the battery.After connect with the battery,the over-current protection and short-circuit protection of Vo1will be disabled.Simple calculation of battery charging time:Battery capacity C(AH)/Charging current(A)Dimensions and Recommended LayoutAttention Matters in Application（1）Output please use wire that cross area is more than2.5mm²,input terminal should add10A/250V AC Fuse.（2）Please correct connection according to the wiring diagram,do not connect wrongly,AC input terminal is strictly prohibited connected with other terminals wrong,otherwise will cause permanent damage to power.（3）Vo2output peak current can not be long term work.（4）To further reduce the Vo1output ripple noise,the user can in the Vo1output parallel connection with one470–1000uF/50V electrolytic capacitor and1uF multilayer ceramic Capacitor.（5）The output of this product is not allowed to work in parallel.（6）The PE terminal of this product should be reliably connected to the earth,in order to improve the capability of anti-interference.（7）Casing will distribute heat when the power is during operating,in order to ensure the power dissipation is good,please keep a certain gap around the power supply to ensure the air flow smoothly,the temperature sensitive device as far as possible from the power.Note:1.Packing information please refer to Product Packing Information which can be downloaded from .Packing bag number:58220041;2.If the product is not operated within the required load range,the product performance cannot be guaranteed to comply with all parameters in the datasheet;3.Unless otherwise specified,parameters in this datasheet were measured under the conditions of Ta=25℃,humidity<75%with nominal input voltage and rated output load;4.All index testing methods in this datasheet are based on our Company’s corporate standards;5.We can provide product customization service,please contact our technicians directly for specific information;6.Specifications are subject to change without prior notice.Mornsun Guangzhou Science&Technology Co.,Ltd.Address:No.5,Kehui St.1,Kehui Development Center,Science Ave.,Guangzhou Science City,Luogang District,Guangzhou,P.R.China Tel:86-20-38601850-8801Fax:86-20-38601272E-mail:***************。

超频三电源基本型号和参数静音电源首选

大理石3003C MA300P规格参数电源简介：大理石3003C版额定功率200W，最大功率300W，提供了1个20+4Pin主板电源接口，2个SATA接口。

另外，大理石3003C配备了超频三专利的120mm液压轴承静音风扇，在最安静的环境下也听不到一点声音，真正带给用户极致的静音享受。

同时，这款产品严格通过了国家3C认证，具有过压，欠压，过温，过流，过载橄榄石370静音版OL370P规格参数电源简介：橄榄石370静音版额定功率270W，符合ATX12V 2.3规范，提供了1个20+4Pin主板电源接口，1个6Pin显卡供电接口，4个SATA接口。

另外，橄榄石370静音版备配超频三专利的120mm液压轴承静音风扇，具有低转速、低噪音特点，在最安静的环境下也听不到一点声音，真正带给用户极致的静音享受。

同时，这款产品严格通过了国家3C认证，具有过压，欠压，过温，过流，过载等保护功能，加上一年换新，三年保修的周到售后服务。

最关键的是，这款电源性价比超高，绝对是学生、家庭、网吧用户首选。

技术、规格参数一览表：适用类型台式机适用平台Intel 双核及AMD双核、三核等处理器额定功率270瓦稳定功率300瓦（可持续24小时运行功率）PFC类型被动式电压范围180V——264V电源规范ATX12V 2.312V输出单路+12V增强输出转换效率75%以上待机功耗小于1瓦热管散热无风扇类型12厘米液压子弹头静音风扇主板供电20+4Pin 线长：420mmCPU供电4+4Pin 线长：420mm显卡供电6Pin 线长：450mmSATA接口4个线长：400+150+150+200mm大4pin接口3个线长：400+150+200mm特色技术ROSH 无铅制程、待机小于1瓦、液压子弹头静音风扇功能保护过压、欠压、过载、过流、过温、短路等保护功能安全认证3C、CE、ROSH 无铅制程平均无故障时间50000小时售后服务一年换新，三年保修适用范围Intel 双核及AMD双核、三核等处理器H3专业版H3-300-12规格参数电源简介：H3专业版是超频三为网吧用户量身打造的一款集节能、静音、稳定于一身的新型专业电源，以率先提供震撼业界的“三年换新”金牌服务和行业一流的顶级品质，完美贴合网吧用户需求。

一般的CPU故障有以下几种

一般的CPU故障有以下几种：散热故障、重启故障、黑屏故障及超频故障(当然CPU go to die 就不算了)。

一、CPU针脚接触不良，导致机器无法启动一般表现在突然无法开机，屏幕无显示信号输出，排除显卡、显示器无问题后，拔下插在主板上的CPU，仔细观察并无烧毁痕迹，但就是无法点亮机器。

后来发现CPU的针脚均发黑、发绿，有氧化的痕迹和锈迹，便用牙刷对CPU针脚做了清洁工作，然后问题就解决了。

故障的原因可能是因为制冷片将芯片的表面温度降得太低，低过了结露点，导致CPU长期工作在潮湿环境中。

而裸露的铜针脚在此环境中与空气中的氧气发生反应生成了铜锈。

日积月累锈斑太多造成接触不良，从而引发故障。

此外还有一些劣质主板，由于CPU插槽质量不好，也会造成接触不良，很多资料上都有此问题，最好的办法就是自己手动安装和固定CPU！二、挂起模式造成CPU烧毁一般的系统挂起并不会造成CPU烧毁，系统会自动降低CPU工作频率和风扇转速来节省能耗。

而挂起模式造成CPU被烧毁，均是超频后的CPU。

这全都因为风扇停止运转造成的。

主板上的监控芯片除可以监控风扇转速外，有的还能在系统进入Suspend（挂起）省电模式下，自动降低风扇转速甚至完全停止运转，这本是好意，可以省电，也可以延长风扇的寿命与使用时间。

过去的CPU处于闲置状态下，热量不高，所以风扇不转，只靠散热片还能应付散热。

但现在的CPU频率实在太高，即使进入挂起模式，当风扇不转时，CPU也会热得发烫。

这种情况并不是在每块主板都会发生，发生时必须要符合三个条件。

首先CPU风扇必须是3pin风扇，这样才会被主板所控制。

第二，主板的监控功能必须具备Fan Off When Suspend （进入挂起模式即关闭风扇电源），且此功能预设为On。

有的主板预设On，甚至有的在Power Management的设定就有Fan Off When Suspend这一项选项，大家可以注意看看。

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10.3
满载下的 SR 软启动.........................................................................................16
10.4
零电压开关 ..............................................................................................................17
5
PCB 布局图——顶层...............................................................8
6
PCB 布局图——底层......................................................... 8
7
元件表 .................................................................. 9
0R 1M5/1%
0805r 0805r 0805r 0805r 0805r 0805r 0805r 0805r 1206R
电阻器
1
电阻器
1
电阻器
1
电阻器
10
2012-05-07
R211 R212 R213,
110k/1% 200R 1M0
0805r 1206R 0805r
电阻器
1
电阻器
1
电阻器
2
R214 R215 R216 R217 R218 R219 R220 R221 R222 R223,
2M0 24k/1%
NC 51k/1%
100k 820R N.C.
二极管
4
光耦合器
1
1
半桥驱动器
1
应用说明
9
2012-05-07
IC201
IC300 L100 Q100, Q102 Q101, Q103 Q104, Q107 Q105, Q106 R100, R104, R109, R111, R112 R101, R103, R105, R108 R102, R107 R106, R113 R110 R114, R115 R116 R117 R118 R119 R120 R121 R122 R123 R124 R125 R200, R202 R201, R203 R205 R206 R207 R208 R209 R210
10.5
主欠压保护............................................................. ......................................18
10.6
动态负载响应 ........................................................................................................ ......19
470k
SOL-20 SO-8 RM10 T0-220
TO-263
SOT-89
SOT-89
1206R
1206R
1206R
1206R
1206 1206R
1206R 1206R 1206R 1206R 1206R 1206R 1206R 1206R 1206R 1206R 0805r
0805r
0805r 0805r 0805r 0805r 0805r 0805r
ICE2HS01G UCC27324_1 40uH//RM10 IPA60R199C6
IPB011N04N
BCX56
BC53
10R
10k
1R0
2k0
10R 4k7
560 3k9 56R 11k 2k7 0R 820 2k2 NC 3k6 10R
11k
0M2 5k6/1% 12k/0.1%
240k 150k/1%
8
磁性元件...................................................... 11
8.1
主变压器 .........................................................................................................................11
本应用说明分享了评估板的电路原理图、PCB 布局图和 BOM，接着介绍了评估板的性能，例如效率和操作波形。如需了解此变换器的详细逐步设计流程，请参考我们的设计指南。
2 评估板
技术规格输入电压 Vin 输出电压和输出电流 Vo ，I o 输出功率 Pin
效率
谐振频率 f r
400VDC 12VDC, 25A
10.7
保持时间测定............................................................................... ............................. ............. 20
应用说明
5
2012-05-07
EVAL2HS01G300W 修订历史：先前版本：
2012-05 NA
V2.0
带 LLC 控制器 ICE2HS01G 的 300W LLC 评估板英飞凌科技亚太私人有限公司 (Infineon Technologies Asia Pacific Pte Ltd) 许可 Li Dong Ke Chunshan
应用说明， V 1 .1，2012 年 5 月
EVAL-2HS01G-300W
带 LLC 控制器 ICE2HS01G 的 300W LLC 评估板
电源管理与供电
思想永不停歇。
版本 2012-05-07 由 Infineon Technologies Asia Pacific 出版 168 Kallang Way, 349253 Singapore, Singapore © Infineon Technologies AP 2010。保留所有权利。
~ 300W 100% 负载时 > 97% 50% 负载时 > 97% 20% 负载时 > 96% 85kHz
应用说明
5
2012-05-07
3 控制电路图
应用说明
6
2012-05-07
4 电源电路图
应用说明
7
2012-05-07
5
PCB 布局图——顶层
6
PCB 布局图——底层
应用说明
8
2012-05-07
请注意！本文档提供的信息仅用于描述某些元件，不得将其视为对特征的担保。保留在交货条款和技术方面进行变更的权利。我们特此声明不作任何及所有形式的担保，包括但不限于涉及本文所述的电路、描述和图表的非侵权担保。
信息有关技术、交货条款及条件和价格的更多信息，请与您最近的英飞凌科技公司办事处 () 联系。
1
谐振模式控制器
1
扼流圈
1
金氧半场效晶体管
2
金氧半场效晶体管
2
NPN 晶体管
2
PNP 晶体管
2
电阻器
5
电阻器
4
电阻器
2
电阻器
2
电阻器
1
电阻器
2
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
2
电阻器
2
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
电阻器
1
Application Note
技术规格................................................................ 5
3
控制电路图 ..................................................... 6
4
电源电路图 ..................................................... 7
1 引言
本文所述的评估板是一种输入电压为 400VDC，输出电压为 12V 的 300W LLC 变换器。它由英飞凌的第二代半桥 LLC 控制器 ICE2HS01G 控制。ICE2HS01G 专为高效应用而设计，具有二次侧同步整流 (SR) 控制功能。这种新的驱动技术使通过二次开关电流操作的半桥 LLC 变换器在 CCM 和 DCM 条件下均可实现 SR。
SFH617A-2 TL431
IC-ST-L6385
DIP4/10 TO92-CBE
SO-8
描述 2 盎司铜铝电解质陶瓷
陶瓷铝电解质
陶瓷铝电解质
数量 1 1 2
1 1 1 5
陶瓷
2
陶瓷
1
陶瓷1陶瓷1 Nhomakorabea陶瓷
2
铝电解质
1
0
铝电解质
1
陶瓷
3
陶瓷
3
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
陶瓷
1
10.1
满载和轻载条件下的软启动..........................................................................................14